DETAILED ACTION
Notice of Pre-AIA or AIA Status
The present application, filed on or after March 16, 2013, is being examined under the first inventor to file provisions of the AIA .
This office action is in response to the filling of the Amendment filed on 05/19/2026.
Claim Objections
Claim 21 is objected to because of the following informalities: Claim 21, line 8 recites “the discharge enable signal”, which should be –a discharge enable signal -- because this term was not previously presented in the claim.
Appropriate correction is required.
Claim Rejections - 35 USC § 103
The following is a quotation of 35 U.S.C. 103 which forms the basis for all obviousness rejections set forth in this Office action:
A patent for a claimed invention may not be obtained, notwithstanding that the claimed invention is not identically disclosed as set forth in section 102 of this title, if the differences between the claimed invention and the prior art are such that the claimed invention as a whole would have been obvious before the effective filing date of the claimed invention to a person having ordinary skill in the art to which the claimed invention pertains. Patentability shall not be negated by the manner in which the invention was made.
Claims 1, 2, 10, 14-16, 20, 21 and 25-27 are rejected under 35 U.S.C. 103 as being unpatentable over Wu et al. (US 2011/0103098), hereinafter Wu, in view of Ausseresse et al (US 2018/0337606), hereinafter Ausseresse, and further in view of Li et al. (US 10,181,804), hereinafter Li.
Regarding claim 1, Wu discloses (see figures 1-9) a protection circuit (figure 1, part 107) of a converter (figure 1, part 101), wherein the converter (figure 1, part 101) (figure 8A, part 800) comprises a transformer (figure 8A, part T), a first switch transistor (figure 8A, part Q1) and a second switch transistor (figure 8A, part Q3) located at a primary edge of the transformer (figure 8A, part primary edge of T) and connected (figure 8A, part Q1/Q3) between an input terminal of the converter (figure 8A, part Vin terminal) and a reference ground (figure 8A, part ground), and a first capacitor (figure 8A, part Cr) and a first inductor (figure 8A, part Lr) forming a resonance circuit (figure 8A, part Cr/Lr) when the second switch transistor is turned on (figure 8A, part Q3; turn-on) (paragraph [0046]; FIG. 8A shows a circuit diagram of a resonant converter resetting system including a series resonant converter 800), and the protection circuit (figure 1, part 107) comprises: an active discharge module (figure 8A, part active discharge module generated by R and Qs), connected to at least one terminal of the first capacitor (figure 8A, part right terminal of Cr; through Lm) to provide a discharge path (figure 8A, part discharge path through Cr, Lm and R), and controlling turning-on and turning-off (figure 8A, part through on/off of Qs) of the discharge path (figure 8A, part discharge path through Cr, Lm and R) according to a discharge enabling signal (figure 8A, part discharge enabling signal that control Qs), wherein in a normal work state (figure 2A, part normal work state) of the converter (figure 8A, part 800) (paragraph [0026]; FIG. 2B shows waveforms of the resonant converter 200 operating under a normal operation), the discharge path (figure 8A, part discharge path through Cr, Lm and R) in the active discharge module (figure 8A, part active discharge module generated by R and Qs) is disconnected (figure 8A, part disconnected when Qs is turned-on and short R), and the first capacitor (figure 8A, part Cr) works as a resonance capacitor (figure 8A, part Cr; normal operation without R); before the converter (figure 8A, part 800) is restarted (figure 8B, part before restarted after t2), the discharge path (figure 8A, part discharge path through Cr, Lm and R) in the active discharge module (figure 8A, part active discharge module generated by R and Qs) is turned on (figure 8A, part turned on when Qs is turned off) for a predetermined time period (figure 8B, part predetermined time period between t1-t2) to release charges stored in the first capacitor (figure 8A, part Cr; through R), and reduces resonance current after the converter (figure 8A, part 800) is restarted (figure 8B, part restarted after t2) to a safe work current of the second switch transistor (figure 8A, part Q3) (paragraph [0046]; the series resonant converter 800 includes a driver which includes a control module coupled to the resistor R and the switch Qs. During the interval t1-t2, either (1) Q3/Q4 are turned on while Q1/Q2 are turn off, or (2) Q1/Q2 are turned on while Q3/Q4 are turn off. Meanwhile, the switch Qs is turned off (i.e., open) by the control module, the resistor R thus consumes resonant tank energy while Q1-Q4 are in a normal operation. To restart the normal operation at t2 with a zero initial condition, Qs is turned on (i.e., close) by the control module to bypass the resistor R), wherein, the active discharge module (figure 8A, part active discharge module generated by R and Qs) comprises a discharge transistor (figure 8A, part Qs), and when the discharge transistor operates (figure 8A, part Qs; operates at turn-off) for turning on the discharge path (figures 8A and 8B, part turning on the discharge path through Cr, Lm and R; when Qs is turned off between t1-t2), the converter is in a stopped work state (figure 8B, part stopped work state after To [shut down point of normal operation of the converter]) (paragraph [0029]; After the resonant converter 200 [800] turns off at t0' [to] (a shut down time point 241), the resonant converter 200 restarts at t1' [after t2] (a restart time point 243). This shunt-down scenario may be triggered to protect the circuit).
Wu does not expressly disclose a flyback converter; and when the discharge transistor operates in an on state for turning on the discharge path, the flyback converter is in a stopped work state and has entered the stopped work state for at least one switch cycle.
Ausseresse teaches (see figures 1-14) a flyback converter (figure 1C) (paragraph [0031]; APWM HB flyback converters), wherein the flyback converter (figure 1C) comprises a transformer (figure 1C, part T1), a first switch transistor (figure 1C, part 12) and a second switch transistor (figure 1C, part 11) located at a primary edge of the transformer (figure 1C, part 13) and connected between an input terminal (figure 1C, part Vin terminal) of the flyback converter (figure 1C) and a reference ground (figure 1C, part ground), and a first capacitor (figure 1C, part Cr) and a first inductor (figure 1C, part Lr) forming a resonance circuit (figure 1C, part Cr/Lr) when the second switch transistor is turned on (figure 1C, part 11; turned-on).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse, because the combination result in more efficient and reliable power converter with more protection for the components.
Li teaches (see figures 1-10) the active discharge module (figure 2, part active discharge module generated by Rs and Qb) comprises a discharge transistor (figure 2, part Qb), and when the discharge transistor operates in an on state (figures 2 and 3A, part Qb; on-state) for turning on the discharge path (figures 2 and 3A, part discharge path generated through Rs and Qb to ground), the converter (figure 2, part 200) is in a stopped work state (figures 2 and 3A, part 200; stopped work state when stop switching operation of Q1/Q2) and has entered the stopped work state for at least one switch cycle (figures 2 and 3A, part 200; stopped work state when stop switching operation of Q1/Q2) (column 5; lines 6-21; Resonant power converter 200 may include, as depicted in FIG. 2, a control circuit 208 configured to switch the converter between an operational mode in which auxiliary soft-start bypass drive circuit 202 is deactivated and the Q1 and Q2 of switching bridge 204 are switched according to a switching cycle (e.g., to provide a first frequency-responsive power through the resonant circuit 206), and a soft-start mode in which the auxiliary soft-start bypass drive circuit 202 is activated).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the combination of Wu and Ausseresse with the discharge transistor features as taught by Li and obtain a protection circuit of a flyback converter, wherein the flyback converter comprises a transformer, a first switch transistor and a second switch transistor located at a primary edge of the transformer and connected between an input terminal of the flyback converter and a reference ground, and a first capacitor and a first inductor forming a resonance circuit when the second switch transistor is turned on, and the protection circuit comprises: an active discharge module, connected to at least one terminal of the first capacitor to provide a discharge path, and controlling turning-on and turning-off of the discharge path according to a discharge enabling signal, wherein in a normal work state of the flyback converter, the discharge path in the active discharge module is disconnected, and the first capacitor works as a resonance capacitor; before the flyback converter is restarted, the discharge path in the active discharge module is turned on for a predetermined time period to release charges stored in the first capacitor, and reduces resonance current after the flyback converter is restarted to a safe work current of the second switch transistor, wherein, the active discharge module comprises a discharge transistor, and when the discharge transistor operates in an on state for turning on the discharge path, the flyback converter is in a stopped work state and has entered the stopped work state for at least one switch cycle, because it provides more efficient and reliable power conversion with effectively limiting high in-rush current and high voltage, without adding considerable power loss, solution size, cost and complexity (column 1; lines 29-33).
Regarding claim 2, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 1). Further, Wu discloses (see figures 1-9) the discharge transistor (figure 8A, part Qs) works in linear region or saturation region (figure 8A, part Qs; linear region or saturation region).
Regarding claim 10, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 1). Further, Wu discloses (see figures 1-9) the first switch transistor (figure 8A, part Q1) and the second switch transistor (figure 8A, part Q3) are sequentially connected in series between the input terminal of the converter (figure 8A, part Vin terminal) and the reference ground (figure 8A, part ground). However, Wu does not expressly disclose the flyback converter.
Ausseresse teaches (see figures 1-14) the first switch transistor (figure 1B, part 11) and the second switch transistor (figure 1B, part 12) are sequentially connected in series between the input terminal of the flyback converter (figure 1B, part Vin terminal) and the reference ground (figure 1B, part ground), or wherein the second switch transistor (figure 1C, part 11) and the first switch transistor (figure 1C, part 12) are sequentially connected in series between the input terminal of the flyback converter (figure 1C, part Vin terminal) and the reference ground (figure 1C, part ground) (paragraph [0031]; APWM HB flyback converters).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse and obtain the first switch transistor and the second switch transistor are sequentially connected in series between the input terminal of the flyback converter and the reference ground, or wherein the second switch transistor and the first switch transistor are sequentially connected in series between the input terminal of the flyback converter and the reference ground, because the combination result in more efficient and reliable power converter with more protection for the components.
Regarding claim 14, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 1). Further, Wu discloses (see figures 1-9) a discharge control circuit (figure 1, part discharge control circuit inside 107) (figure 8A, part discharge control circuit that control Qs), connected to the active discharge module (figure 8A, part active discharge module generated by R and Qs), and generating the discharge enabling signal (figure 8A, part discharge enabling signal that control Qs) of a corresponding effective state according to the work state (figure 8B, part according to work state) of the converter (figure 8A, part 800) (paragraph [0046]; the series resonant converter 800 includes a driver which includes a control module coupled to the resistor R and the switch Qs. During the interval t1-t2, either (1) Q3/Q4 are turned on while Q1/Q2 are turn off, or (2) Q1/Q2 are turned on while Q3/Q4 are turn off. Meanwhile, the switch Qs is turned off (i.e., open) by the control module, the resistor R thus consumes resonant tank energy while Q1-Q4 are in a normal operation. To restart the normal operation at t2 with a zero initial condition, Qs is turned on (i.e., close) by the control module to bypass the resistor R). However, Wu does not expressly disclose the flyback converter.
Ausseresse teaches (see figures 1-14) the flyback converter (figure 1C) (paragraph [0031]; APWM HB flyback converters).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse, because the combination result in more efficient and reliable power converter with more protection for the components.
Regarding claim 15, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 14). Further, Wu discloses (see figures 1-9) the discharge control circuit (figure 1, part discharge control circuit inside 107) (figure 8A, part discharge control circuit that control Qs) comprises: a detection module (figure 4A, part 401), for detecting the work state (figure 8B, part work state) of the converter (figure 8A, part 800), and generating a turning-on signal (figure 4A, part turning-on signal Y; to consume the resonant energy) and a turning-off signal (figure 4A, part turning-off signal N) before the converter (figure 8A, part 800) is restarted (figure 8B, part before restarted after t2); and control logics (figure 4A, part 407), for generating the discharge enabling signal (figure 8A, part discharge enabling signal that control Qs) according to the turning-on signal (figure 4A, part turning-on signal Y) and the turning-off signal (figure 4A, part turning-off signal N) (paragraphs [0032] and [0046]; a driving process 400 of the energy resetting module 107 is introduced to reset the resonant network energy before restarting the resonant converter 200. FIG. 4A shows an operational diagram of the process 400, in accordance with an exemplary embodiment. In particular, the driving process 400 starts from a startup 401 and determines whether the resonant converter 200 is shutting down or not… the series resonant converter 800 includes a driver which includes a control module coupled to the resistor R and the switch Qs. During the interval t1-t2, either (1) Q3/Q4 are turned on while Q1/Q2 are turn off, or (2) Q1/Q2 are turned on while Q3/Q4 are turn off. Meanwhile, the switch Qs is turned off (i.e., open) by the control module, the resistor R thus consumes resonant tank energy while Q1-Q4 are in a normal operation. To restart the normal operation at t2 with a zero initial condition, Qs is turned on (i.e., close) by the control module to bypass the resistor R). However, Wu does not expressly disclose the flyback converter.
Ausseresse teaches (see figures 1-14) the flyback converter (figure 1C) (paragraph [0031]; APWM HB flyback converters).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse, because the combination result in more efficient and reliable power converter with more protection for the components.
Regarding claim 16, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 14). Further, Wu discloses (see figures 1-9) the discharge control circuit (figure 1, part discharge control circuit inside 107) (figure 8A, part discharge control circuit that control Qs) comprises: a detection module (figure 4A, part 401), for detecting the work state (figure 8B, part work state) of the converter (figure 8A, part 800), and generating a tuning-on signal (figure 4A, part turning-on signal Y; to consume the resonant energy) before the converter (figure 8A, part 800) is restarted (figure 8B, part before restarted after t2); a time delay module (figure 4A, part time delay module at 403), for starting a delay (figure 8B, part delay between t1-t2) when the turning-on signal is valid (figure 4A, part turning-on signal Y; to consume the resonant energy), and generating a turning-off signal (figure 4A, part turning-off signal N) when the delay reaches the predetermined time period (figure 8B, part at t2); and control logics (figure 4A, part 407), for generating the discharge enabling signal (figure 8A, part discharge enabling signal that control Qs) according to the turning-on signal (figure 4A, part turning-on signal Y; to consume the resonant energy) and the turning-off signal (figure 4A, part turning-off signal N) (paragraphs [0032] and [0046]; a driving process 400 of the energy resetting module 107 is introduced to reset the resonant network energy before restarting the resonant converter 200. FIG. 4A shows an operational diagram of the process 400, in accordance with an exemplary embodiment. In particular, the driving process 400 starts from a startup 401 and determines whether the resonant converter 200 is shutting down or not… the series resonant converter 800 includes a driver which includes a control module coupled to the resistor R and the switch Qs. During the interval t1-t2, either (1) Q3/Q4 are turned on while Q1/Q2 are turn off, or (2) Q1/Q2 are turned on while Q3/Q4 are turn off. Meanwhile, the switch Qs is turned off (i.e., open) by the control module, the resistor R thus consumes resonant tank energy while Q1-Q4 are in a normal operation. To restart the normal operation at t2 with a zero initial condition, Qs is turned on (i.e., close) by the control module to bypass the resistor R). However, Wu does not expressly disclose the flyback converter.
Ausseresse teaches (see figures 1-14) the flyback converter (figure 1C) (paragraph [0031]; APWM HB flyback converters).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse, because the combination result in more efficient and reliable power converter with more protection for the components.
Regarding claim 20, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 16). Further, Wu discloses (see figures 1-9) the detection module (figure 4A, part 401) receives a system power-on signal (figure 4A, part startup signal), and turns on (figure 8A, part turned on when Qs is turned off) the discharge path (figure 8A, part discharge path through Cr, Lm and R) in the active discharge module (figure 8A, part active discharge module generated by R and Qs) for the predetermined time period (figure 8B, part predetermined time period between t1-t2) before system restart event is finished (figure 8B, part before restarted after t2) (paragraph [0046]; the series resonant converter 800 includes a driver which includes a control module coupled to the resistor R and the switch Qs. During the interval t1-t2, either (1) Q3/Q4 are turned on while Q1/Q2 are turn off, or (2) Q1/Q2 are turned on while Q3/Q4 are turn off. Meanwhile, the switch Qs is turned off (i.e., open) by the control module, the resistor R thus consumes resonant tank energy while Q1-Q4 are in a normal operation. To restart the normal operation at t2 with a zero initial condition, Qs is turned on (i.e., close) by the control module to bypass the resistor R).
Regarding claim 21, claim 1 has the same limitations, except that is not a method claim, based on this is rejected for the same reasons.
Regarding claim 25, claim 15 has the same limitations, except that is not a method claim, based on this is rejected for the same reasons.
Regarding claim 26, claim 16 has the same limitations, except that is not a method claim, based on this is rejected for the same reasons.
Regarding claim 27, claim 20 has the same limitations, except that is not a method claim, based on this is rejected for the same reasons.
Claims 3, 6 and 22-24 are rejected under 35 U.S.C. 103 as being unpatentable over Wu et al. (US 2011/0103098), hereinafter Wu, in view of Ausseresse et al (US 2018/0337606), hereinafter Ausseresse, and further in view of Li et al. (US 10,181,804), hereinafter Li, and further in view of Katsumi (JPH02106164; rejection based on English translation), hereinafter Katsumi.
Regarding claim 3, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 2). Further, Wu discloses (see figures 1-9) the active discharge module (figure 8A, part active discharge module generated by R and Qs) further comprises a first resistor (figure 8A, part R), and the discharge transistor (figure 8A, part Qs). However, Wu does not expressly disclose a third switch transistor connected in series with the first resistor.
Katsumi teaches (see figures 1-5) the active discharge module (figure 1, part active discharge module generated by 14 and 15) further comprises a first resistor (figure 1, part 14), and the discharge transistor (figure 1, part 15) is a third switch transistor (figure 1, part 15) connected in series with the first resistor (figure 1, part 14) (paragraph [0001]; DESCRIPTION OF THE PREFERRED EMBODIMENTS; second sentence; In FIG. 1, reference numeral 14 denotes a discharging resistor, which is connected in parallel to the resonance capacitor 8 via a switching element 15).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the active discharge module of Wu with the active discharge module features as taught Katsumi, because it provides more reliable and protected converter with more efficient and accurate discharge module that reduce the resonance current (Abstract).
Regarding claim 6, Wu, Ausseresse, Li and Katsumi teach everything claimed as applied above (see claim 3). Further, Wu discloses (see figures 1-9) discharge path (figure 8A, part discharge path through Cr, Lm and R) and the first capacitor (figure 8A, part Cr). However, Wu does not expressly disclose discharge path is provided between the first terminal and a second terminal of the first capacitor, and the third switch transistor and the first resistor are connected in series between the first terminal and the second terminal of the first capacitor.
Katsumi teaches (see figures 1-5) a discharge path (figure 1, part discharge path generated by 14 and 15) is provided between the first terminal and a second terminal of the first capacitor (figure 1, part 8), and the third switch transistor (figure 1, part 15) and the first resistor are connected in series (figure 1, part 14) between the first terminal and the second terminal of the first capacitor (figure 1, part 8) (paragraph [0001]; DESCRIPTION OF THE PREFERRED EMBODIMENTS; second sentence; In FIG. 1, reference numeral 14 denotes a discharging resistor, which is connected in parallel to the resonance capacitor 8 via a switching element 15).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the active discharge module of Wu with the active discharge module features as taught Katsumi, because it provides more reliable and protected converter with more efficient and accurate discharge module that reduce the resonance current (Abstract).
Regarding claim 22, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 21). Further, Wu discloses (see figures 1-9) wherein the discharge path (figure 8A, part discharge path through Cr, Lm and R). However, Wu does not expressly disclose the discharge path is located in a discharge path between a first terminal and a second terminal of the first capacitor.
Katsumi teaches (see figures 1-5) the discharge path (figure 1, part discharge path generated by 14 and 15) is located in a discharge path (figure 1, part discharge path generated by 14 and 15) between a first terminal and a second terminal of the first capacitor (figure 1, part 8) (paragraph [0001]; DESCRIPTION OF THE PREFERRED EMBODIMENTS; second sentence; In FIG. 1, reference numeral 14 denotes a discharging resistor, which is connected in parallel to the resonance capacitor 8 via a switching element 15).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the active discharge module of Wu with the active discharge module features as taught Katsumi, because it provides more reliable and protected converter with more efficient and accurate discharge module that reduce the resonance current (Abstract).
Regarding claim 23, Wu, Ausseresse, Li and Katsumi teach everything claimed as applied above (see claim 22). Further, Wu discloses (see figures 1-9) the first capacitor (figure 8A, part Cr), the first switch transistor (figure 8A, part Q1) and the second switch transistor (figure 8A, part Q3). However, Wu does not expressly disclose the second terminal of the first capacitor is connected to an intermediate node of the first switch transistor and the second switch transistor, and the second terminal of the first capacitor has floating ground voltage when the first switch transistor is in a turned-off state.
Ausseresse teaches (see figures 1-14) the second terminal of the first capacitor (figure 1C, part lower terminal of 15) is connected to an intermediate node of the first switch transistor (figure 1C, part 12) and the second switch transistor (figure 1C, part 11), and the second terminal of the first capacitor has floating ground voltage figure 1C, part lower terminal of 15) when the first switch transistor is in a turned-off state (figure 1C, part 12; turned-off).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse and obtain the second terminal of the first capacitor is connected to an intermediate node of the first switch transistor and the second switch transistor, and the second terminal of the first capacitor has floating ground voltage when the first switch transistor is in a turned-off state, because the combination result in more efficient and reliable power converter with more protection for the components.
Regarding claim 24, Wu, Ausseresse, Li and Katsumi teach everything claimed as applied above (see claim 23). Further, Wu discloses (see figures 1-9) converting the discharge enabling signal from a first level (figure 8A, part discharge enabling signal that control Qs; first level) with respect to the reference ground (figure 8A, part discharge enabling signal that control Qs; with respect to ground) to a second level (figure 8A, part discharge enabling signal that control Qs; second level). However, Wu does not expressly disclose with respect to the floating ground voltage.
Ausseresse teaches (see figures 1-14) the floating ground voltage (figure 1C, part floating ground voltage at lower terminal of 15 when 12 is turned-off).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to apply the protection circuit of Wu to the flyback converter as taught by Ausseresse and obtain converting the discharge enabling signal from a first level with respect to the reference ground to a second level with respect to the floating ground voltage, because the combination result in more efficient and reliable power converter with more protection for the components.
Claims 17-19 are rejected under 35 U.S.C. 103 as being unpatentable over Wu et al. (US 2011/0103098), hereinafter Wu, in view of Ausseresse et al (US 2018/0337606), hereinafter Ausseresse, and further in view of Li et al. (US 10,181,804), hereinafter Li, and further in view of Zeng et al. (US 2007/0285952), hereinafter Zeng.
Regarding claim 17, Wu, Ausseresse and Li teach everything claimed as applied above (see claim 16). Further, Wu discloses (see figures 1-9) the detection module (figure 4A, part 401). However, Wu does not expressly disclose receives a first switch control signal of the first switch transistor and a second switch control signal of the second switch transistor, and generates at least one of the turning-on signal and the turning-off signal according to the first switch control signal and the second switch control signal.
Zeng teaches (see figures 1-9) the detection module (figure 9, part 31) receives a first switch control signal (figure 9, part gQ1) of the first switch transistor (figure 9, part Q1) and a second switch control signal (figure 9, part gQ2) of the second switch transistor (figure 9, part Q2), and generates at least one of the turning-on signal (figure 9, part turn-on signal from 32) and the turning-off signal (figure 9, part turn-off signal from 32) according to the first switch control signal (figure 9, part gQ1) and the second switch control signal (figure 9, part gQ2).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the detection module of Wu with the detection module features as taught Zeng, because it provides more accurate detection of the work state of the circuit in order to obtain more efficient and stable operation (paragraph [0020]).
Regarding claim 18, Wu, Ausseresse, Li and Zeng teach everything claimed as applied above (see claim 17). Further, Wu discloses (see figures 1-9) the detection module (figure 4A, part 401) generates the turning-on signal (figure 4A, part turning-on signal Y; to consume the resonant energy). However, Wu does not expressly disclose when a duration during which both the first switch control signal and the second switch control signal are in invalid state exceeds at least one switch cycle.
Zeng teaches (see figures 1-9) the detection module (figure 9, part 31) generates the turning-on signal (figure 9, part turn-on signal from 32) when a duration during which both the first switch control signal (figure 9, part gQ1) and the second switch control signal (figure 9, part gQ2) are in invalid state exceeds at least one switch cycle (figure 9, part gQ1 and gQ2 are invalid state exceeds at least one switch cycle).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the detection module of Wu with the detection module features as taught Zeng, because it provides more accurate detection of the work state of the circuit in order to obtain more efficient and stable operation (paragraph [0020]).
Regarding claim 19, Wu, Ausseresse, Li and Zeng teach everything claimed as applied above (see claim 17). Further, Wu discloses (see figures 1-9) the detection module (figure 4A, part 401) generates the turning-off signal (figure 4A, part turning-off signal N). However, Wu does not expressly disclose the detection module generates the turning-off signal when it detects a complementary level state of the first switch control signal and the second switch control signal in at least one continuous switch cycle.
Zeng teaches (see figures 1-9) the detection module (figure 9, part 31) generates the turning-off signal (figure 9, part turn-off signal from 32) when it detects a complementary level state of the first switch control signal (figure 9, part gQ1) and the second switch control signal (figure 9, part gQ2) in at least one continuous switch cycle (figure 9, part complementary level state of gQ1 and gQ2 ) in at least one continues switch cycle).
It would have been obvious to one having ordinary skill in the art before the effective filling date of the claimed invention to configure the detection module of Wu with the detection module features as taught Zeng, because it provides more accurate detection of the work state of the circuit in order to obtain more efficient and stable operation (paragraph [0020]).
Response to Arguments
Applicant’s arguments with respect to claims 1 and 21 have been considered but are moot because the new ground of rejection does not rely on any reference applied in the prior rejection of record for any teaching or matter specifically challenged in the argument.
Conclusion
Applicant's amendment necessitated the new ground(s) of rejection presented in this Office action. Accordingly, THIS ACTION IS MADE FINAL. See MPEP § 706.07(a). Applicant is reminded of the extension of time policy as set forth in 37 CFR 1.136(a).
A shortened statutory period for reply to this final action is set to expire THREE MONTHS from the mailing date of this action. In the event a first reply is filed within TWO MONTHS of the mailing date of this final action and the advisory action is not mailed until after the end of the THREE-MONTH shortened statutory period, then the shortened statutory period will expire on the date the advisory action is mailed, and any extension fee pursuant to 37 CFR 1.136(a) will be calculated from the mailing date of the advisory action. In no event, however, will the statutory period for reply expire later than SIX MONTHS from the date of this final action.
Any inquiry concerning this communication or earlier communications from the examiner should be directed to Carlos O. Rivera-Pérez, whose telephone number is (571) 272-2432 and fax is (571) 273-2432. The examiner can normally be reached on Monday through Friday, 8:30 AM – 5:00 PM EST.
If attempts to reach the examiner by telephone are unsuccessful, the examiner’s supervisor, Thienvu V. Tran can be reached on (571) 270-1276. The fax phone number for the organization where this application or proceeding is assigned is 571-273-8300.
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/C.O.R. /
Examiner, Art Unit 2838
/THIENVU V TRAN/ Supervisory Patent Examiner, Art Unit 2838
Prosecution Insights